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MC34067DWR2G 参数 Datasheet PDF下载

MC34067DWR2G图片预览
型号: MC34067DWR2G
PDF下载: 下载PDF文件 查看货源
内容描述: 高性能谐振模式控制器 [High Performance Resonant Mode Controllers]
分类和应用: 控制器
文件页数/大小: 16 页 / 536 K
品牌: ONSEMI [ ONSEMI ]
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MC34067, MC33067  
Error Amplifier  
The minimum frequency is programmed by R  
Equation 1:  
using  
OSC  
A fully accessible high performance Error Amplifier is  
provided for feedback control of the power supply system.  
The Error Amplifier is internally compensated and features  
dc open loop gain greater than 70 dB, input offset voltage of  
less than 10 mV and a guaranteed minimum gain−bandwidth  
product of 2.5 MHz. The input common mode range extends  
from 1.5 V to 5.1 V, which includes the reference voltage.  
1
t
PD  
t
70 ns  
ƒ
(max)  
(min)  
(eq. 1)  
R
=
=
OSC  
5.1  
0.348 C  
C
ȏn  
ǒ3.6Ǔ  
OSC  
OSC  
where tPD is the internal propagation delay.  
The maximum oscillator frequency is set by the current  
through resistor R . The current required to discharge  
VFO  
Oscillator  
Control Current  
C
OSC  
at the maximum oscillator frequency can be calculated  
by Equation 2:  
3.1 V  
3
5.1 − 3.6  
1
ƒ
I
= C  
= 1.5C  
OSC  
I
R
VFO  
(max)  
(max)  
OSC  
OSC  
6
8
7
Error Amp  
Clamp  
(eq. 2)  
ƒ
(max)  
Error Amp Output  
The discharge current through R  
and can be calculated by Equation 3:  
must also be known  
OSC  
Noninverting Input  
Inverting Input  
1
Error  
Amp  
ƒ
(min)  
ǒ Ǔ  
R
C
OSC OSC  
5.1 − 3.6  
ε ǒ  
Ǔ
I
=
R
OSC  
R
(eq. 3)  
OSC  
Figure 17. Error Amplifier and Clamp  
1
ƒ
R
C
(min) OSC OSC  
1.5  
=
ε
When the Error Amplifier output is coupled to the I  
pin by R  
OSC  
R
OSC  
, as illustrated in Figure 17, it provides the  
VFO  
Resistor R  
can now be calculated by Equation 4:  
Oscillator Control Current, I  
. The output swing of the  
VFO  
OSC  
Error Amplifier is restricted by a clamp circuit to improve  
its transient recovery time.  
2.5 − V  
EAsat  
R
=
(eq. 4)  
VFO  
I
I
R
(max)  
OSC  
Output Section  
One−Shot Timer  
The pulse(t ), generated by the Oscillator and One−Shot  
OS  
The One−Shot is designed to disable both outputs  
simultaneously providing a deadtime before either output is  
timer is gated to dual totem−pole output drives by the  
Steering Flip−Flop shown in Figure 18. Positive transitions  
enabled. The One−Shot capacitor (C ) is charged  
of t toggle the Flip−Flop, which causes the pulses to  
T
OS  
concurrently with the oscillator capacitor by transistor Q1,  
as shown in Figure 16. The one−shot period begins when the  
alternate between Output A and Output B. The flip−flop is  
reset by the undervoltage lockout circuit during startup to  
guarantee that the first pulse appears at Output A.  
oscillator comparator turns off Q1, allowing C to  
T
discharge. The period ends when resistor R discharges C  
T
T
to the threshold of the One−Shot comparator. The lower  
threshold of the One−Shot is 3.6 V. By choosing C , R can  
V
CC  
T
T
by solved by Equation 5:  
t
t
OS  
OS  
Output A  
R
=
=
T
(eq. 5)  
5.1  
Steering  
Flip−Flop  
14  
13  
ȏn  
0.348 C  
T
C
ǒ3.6Ǔ  
T
Power Ground  
PWR  
GND  
Q
T
Errors in the threshold voltage and propagation delays  
through the output drivers will affect the One−Shot period.  
To guarantee accuracy, the output pulse of the control chip  
V
Q
CC  
R
is trimmed to within 5% of 250 ns with nominal values of R  
T
Output B  
and C .  
T
12  
The outputs of the Oscillator and One−Shot comparators  
are OR’d together to produce the pulse t , which drives the  
Flip−Flop and output drivers. The output pulse (t ) is  
OS  
PWR  
GND  
OS  
initiated by the Oscillator and terminated by the One−Shot  
comparator. With zero voltage resonant mode converters,  
the oscillator discharge time should never be set less than the  
one−shot period.  
Figure 18. Steering Flip−Flop and Output Drivers  
http://onsemi.com  
9