MIC2584/2585
Micrel
This second timing cycle (t
voltage exceeds its FB pin threshold (V ). See Figure 4 in
) begins when the lagging
Functional Description
Hot Swap Insertion
POR
FB
the "Timing Diagrams". When the power supply is already
present(i.e.,nota“hotswapping”condition)andtheMIC2584/
85 device is enabled by applying a logic high signal at the ON
pin, the GATE outputs begin ramping immediately as the first
CPOR timing cycle is bypassed. Active current regulation is
employedtolimittheinrushcurrenttransientresponseduring
start-up by regulating the load current at the programmed
current limit value (See "Current Limiting and Dual-Level
Circuit Breaker" section). The following equation is used to
determine the nominal current limit value:
When circuit boards are inserted into live system backplanes
and supply voltages, high inrush currents can result due to
the charging of bulk capacitance that resides across the
supply pins of the circuit board. This inrush current, although
transient in nature, may be high enough to cause permanent
damage to on-board components or may cause the system’s
supply voltages to go out of regulation during the transient
period which may result in system failures. The MIC2584 and
MIC2585actasacontrollerforexternalN-ChannelMOSFET
devices in which the gate drive is controlled to provide inrush
currentlimitingandoutputvoltageslewratecontrolduringhot
swap insertions.
V
50mV
TRIPSLOW
I
=
=
LIM
(2)
R
R
SENSE
SENSE
Power Supply
where V
in the electrical table and R
is the current limit slow trip threshold found
TRIPSLOW
VCC1 is the main supply input to the MIC2584/85 controller
with a voltage range of 2.3V to 13.2V. The VCC2 supply input
ranges from 1.0V to 13.2V and must be less than or equal to
VCC1 for operation. Both inputs can withstand transient
spikes up to 20V. In order to ensure stability of the supplies,
a minimum 1µF capacitor from each VCC to ground is
recommended. Alternatively, a low pass filter, shown in the
typical application circuit, can be used to eliminate high
frequency oscillations as well as help suppress transient
spikes.
is the selected value that
SENSE
will set the desired current limit. There are two basic start-up
modes for the MIC2584/85: 1)Start-up dominated by load
capacitance and 2)start-up dominated by total gate capaci-
tance. The magnitude of the inrush current delivered to the
load will determine the dominant mode. If the inrush current
is greater than the programmed current limit (I ), then load
LIM
capacitance is dominant. Otherwise, gate capacitance is
dominant. The expected inrush current may be calculated
using the following equation:
Also, due to the existence of undetermined parasitic induc-
tance in the absence of bulk capacitance, placing a Zener
diode at each VCC of the controller to ground in order to
provide external supply transient protection is strongly rec-
ommended. See the typical application circuit in Figure 1.
C
C
C
C
LOAD
LOAD
INRUSH
where I
I
×
14µA ×
GATE
(3)
is the
GATE
GATE
is the GATE pin pull-up current, C
GATE
LOAD
load capacitance, and C
is the total GATE capacitance
GATE
Start-Up Cycle
(C
of the external MOSFET and any external capacitor
ISS
connected from the MIC2584/85 GATE pin to ground).
Supply Contact Delay
Load Capacitance Dominated Start-Up
DuringahotinsertofaPCboardintoabackplaneorwhenthe
main supply (VCC1) is powered up from a cold start, as the
voltage at the ON pin rises above its threshold (1.235V
typical), the MIC2584/85 first checks that both supply volt-
ages are above their respective UVLO thresholds. If so, then
the device is enabled and an internal 2.5µA current source
In this case, the load capacitance (C
) is large enough to
LOAD
cause the inrush current to exceed the programmed current
limit but is less than the fast-trip threshold (or the fast-trip
threshold is disabled, ‘M’ option). During start-up under this
condition, the load current is regulated at the programmed
begins charging capacitor C
to 0.3V to initiate a start-up
current limit value (I ) and held constant until the output
POR
LIM
sequence. Once the start-up delay (t
CPOR pin is pulled immediately to ground and a separate
14µA current source begins charging each GATE output to
) elapses, the
voltage rises to its final value. The output slew rate and
equivalent GATE voltage slew rate is computed by the
following equation:
START
drive the external MOSFET that switches V to V
programmed contact start-up delay is calculated using the
following equation:
. The
IN
OUT
I
LIM
Output Voltage Slew Rate,dV
/dt =
OUT
(4)
C
LOAD
where I
quently, the value of C
the overcurrent response time, t
is the programmed current limit value. Conse-
VSTART
LIM
tSTART = CPOR
×
0.12 × CPOR (µF)
(1)
must be selected to ensure that
FILTER
ICPOR
, exceeds the time
OCSLOW
where the start-up delay timer threshold (V
) is 0.3V,
) is 2.5µA. See
needed for the output to reach its final value. For example,
given a MOSFET with an input capacitance C = C =
GATE
START
and the Power-On Reset timer current (I
CPOR
ISS
Table 2 for some typical supply contact start-up delays using
2000pF, C
is 1000µF, and I
is set to 5A with a 12V
LOAD
LIM
several standard value capacitors. As each GATE voltage
input, then the load capacitance dominates as determined by
continues ramping toward its final value (V
+ V ) at a
the calculated INRUSH > I . Therefore, the output voltage
CC
GS
LIM
defined slew rate (See Load Capacitance/Gate Capacitance
Dominated Start-Up sections), a second CPOR timing cycle
begins if: 1)/FAULT is high and 2)CFILTER is low (i.e., not an
overvoltage, undervoltage lockout, or overcurrent state).
slew rate determined from Equation 4 is:
5A
V
Output Voltage Slew Rate, (dVOUT/dt) =
= 5
100µF
ms
March 2005
15
MIC2584/2585
MICREL [ MICREL SEMICONDUCTOR ]
