HV9921/HV9922/HV9923
Functional Description
where ITH is the current sense comparator threshold.
The ripple current introduces a peak-to-average error in
the output current setting that needs to be accounted for.
Due to the constant off-time control technique used in the
HV9921/22/23, the ripple current is independent of the input
AC or DC line voltage variation. Therefore, the output current
will remain unaffected by the varying input voltage.
The HV9921/22/23 are PWM peak current controllers
for controlling a buck converter topology in continuous
conduction mode (CCM). The output current is internally
preset at 20mA (HV9921), 50mA (HV9922), or 30mA
(HV9923).
When the input voltage of 20 to 400V appears at the
DRAIN pin, the internal high-voltage linear regulator seeks
to maintain a voltage of 7VDC at the VDD pin. Until this
voltage exceeds the internally programmed under-voltage
threshold, the output switching MOSFET is non-conductive.
When the threshold is exceeded, the MOSFET turns on. The
input current begins to flow into the DRAIN pin. Hysteresis
is provided in the under-voltage comparator to prevent
oscillation.
Adding a filter capacitor across the LED string can reduce
the output current ripple even further, thus permitting a
reduced value of L1. However, one must keep in mind that
the peak-to-average current error is affected by the variation
of T . Therefore, the initial output current accuracy might
be sOaFcFrificed at large ripple current in L1.
Another important aspect of designing an LED driver with the
HV9921/22/23 is related to certain parasitic elements of the
circuit, including distributed coil capacitance of L1, junction
capacitance and reverse recovery of the rectifier diode D1,
capacitance of the printed circuit board traces CPCB and output
capacitance CDRAIN of the controller itself. These parasitic
elements affect the efficiency of the switching converter and
could potentially cause false triggering of the current sense
comparator if not properly managed. Minimizing these
parasitics is essential for efficient and reliable operation of
the HV9921/22/23.
When the input current exceeds the internal preset level,
a current sense comparator resets an RS flip-flop, and the
MOSFET turns off. At the same time, a one-shot circuit
is activated that determines the duration of the off-state
(10.5µS typ.). As soon as this time is over, the flip-flop sets
again. The new switching cycle begins.
A “blanking” delay of 300nS is provided that prevents false
triggering of the current sense comparator due to the leading
edge spike caused by circuit parasitics.
Coil capacitance of inductors is typically provided in the
manufacturer’s data books either directly or in terms of the
self-resonant frequency (SRF).
SRF = 1/(2π L ⋅CL )
Application Information
The HV9921/22/23 is a low-cost off-line buck converter IC
specifically designed for driving multi-LED strings. It can be
operated from either universalAC line range of 85 to 264VAC,
or 20 to 400VDC, and drives up to tens of high brightness
LEDs. All LEDs can be run in series, and the HV9921/22/23
regulates at constant current, yielding uniform illumination.
The HV9921/22/23 is compatible with triac dimmers. The
output current is internally fixed at 20mA for the HV9921,
50mA for the HV9922, and 30mA for HV9923. These parts
are available in space saving TO-92 and SOT-89 packages.
where L is the inductance value, and CL is the coil
capacitance.) Charging and discharging this capacitance
every switching cycle causes high-current spikes in the LED
string. Therefore, connecting a small capacitor CO (~10nF) is
recommended to bypass these spikes.
Using an ultra-fast rectifier diode for D1 is recommended
to achieve high efficiency and reduce the risk of false
triggering of the current sense comparator. Using diodes
with shorter reverse recovery time trr and lower junction
capacitance CJ achieves better performance. The reverse
voltage rating V of the diode must be greater than the
maximum input Rvoltage of the LED lamp.
Selecting L1 and D1
There is a certain trade-off to be considered between
optimal sizing of the output inductor L1 and the tolerated
output current ripple. The required value of L1 is inversely
proportional to the ripple current ∆IO in it.
The total parasitic capacitance present at the DRAIN pin of
the HV9921/22/23 can be calculated as:
VO ⋅TOFF
(1)
L1 =
(3)
CP = CDRAIN + CPCB + CL + CJ
∆IO
When the switching MOSFET turns on, the capacitance CP
is discharged into the DRAIN pin of the IC. The discharge
current is limited to about 150mA typically. However, it
may become lower at increased junction temperature. The
duration of the leading edge current spike can be estimated
VO is the forward voltage of the LED string. T
is the off-
time of the HV9921/22/23. The output currenOtFFin the LED
string (IO) is calculated then as:
1
(2)
IO = ITH − ⋅ ∆IO
2
NR092005
5
SUPERTEX [ Supertex, Inc ]
