Hig h -Effic ie n c y, P WM, S t e p -Do w n
DC-DC Co n t ro lle rs in 1 6 -P in QS OP
AC current to DC load current. A higher value of LIR
__________________De s ig n P ro c e d u re
allows smaller inductance, but results in higher losses
and ripple. A good compromise between size and loss-
es is found at a 30% ripple current to load current ratio
(LIR = 0.3), which corresponds to a peak inductor cur-
rent 1.15 times higher than the DC load current.
The predesigned standard application circuits (Figure
1 and Table 1) contain ready-to-use solutions for com-
mon applications. Use the following design procedure
to optimize the basic schematic for different voltage or
current requirements. Before beginning a design, firmly
establish the following:
V
(V
- V
)
OUT IN(MAX)
OUT
L = ———————————
x f x I x LIR
V , the maximum input (battery) voltage. This
IN(MAX)
V
OUT
IN(MAX)
value should include the worst-case conditions, such
as no-load operation when a battery charger or AC
a d a p te r is c onne c te d b ut no b a tte ry is ins ta lle d .
where:
f = switching frequency, normally 150kHz or
300kHz
I
= maximum DC load current
OUT
V
must not exceed 30V. This 30V upper limit is
IN(MAX)
LIR = ratio of AC to DC inductor current,
typically 0.3
determined by the breakdown voltage of the BST float-
ing gate driver to GND (36V absolute maximum).
The peak inductor current at full load is 1.15 x I
the above equation is used; otherwise, the peak current
can be calculated by:
if
OUT
V
, the minimum input (battery) voltage. This
IN(MIN)
should be at full-load under the lowest battery condi-
tions. If V is less than 4.5V, a special circuit must
IN(MIN)
be used to externally hold up VL above 4.8V. If the min-
imum input-output difference is less than 1V, the filter
capacitance required to maintain good AC load regula-
tion increases.
V
(V
- V
)
2–MAX165
OUT IN(MAX)
OUT
I
= I
+
PEAK
LOAD
2 x f x L x V
IN(MAX)
The inductor’s DC resistance is a key parameter for effi-
ciency performance and must be ruthlessly minimized,
In d u c t o r Va lu e
The e xa c t ind uc tor va lue is n’t c ritic a l a nd c a n b e
adjusted freely in order to make trade-offs among size,
cost, and efficiency. Although lower inductor values will
minimize size and cost, they will also reduce efficiency
due to higher peak currents. To permit use of the physi-
cally smallest inductor, lower the inductance until the
circuit is operating at the border between continuous
and discontinuous modes. Reducing the inductor value
even further, below this crossover point, results in dis-
continuous-conduction operation even at full load. This
helps reduce output filter capacitance requirements but
c a us e s the c ore e ne rg y s tora g e re q uire me nts to
increase again. On the other hand, higher inductor val-
ues will increase efficiency, but at some point resistive
losses due to extra turns of wire will exceed the benefit
gained from lower AC current levels. Also, high induc-
preferably to less than 25mΩ at I
= 3A. If a stan-
OUT
dard off-the-shelf inductor is not available, choose a
2
2
core with an LI rating greater than L x I
and wind
PEAK
it with the largest diameter wire that fits the winding
area. For 300kHz applications, ferrite core material is
strongly preferred; for 150kHz applications, Kool-mu
(a luminum a lloy) a nd e ve n p owd e re d iron c a n b e
acceptable. If light-load efficiency is unimportant (in
desktop 5V-to-3V applications, for example) then low-
permeability iron-powder cores may be acceptable,
even at 300kHz. For high-current applications, shielded
core geometries (such as toroidal or pot core) help
keep noise, EMI, and switching-waveform jitter low.
Cu rre n t -S e n s e Re s is t o r Va lu e
The current-sense resistor value is calculated accord-
ing to the worst-case, low-current-limit threshold voltage
(from the Electrical Characteristics table) and the peak
inductor current. The continuous-mode peak inductor-
current calculations that follow are also useful for sizing
the switches and specifying the inductor-current satu-
tor values affect load-transient response; see the V
SAG
equation in the Low-Voltage Operation section.
The following equations are given for continuous-conduc-
tion operation since the MAX1652 family is mainly intend-
ed for high-efficiency, battery-powered applications. See
Appendix A in Maxim’s Battery Management and DC-DC
Converter Circuit Collection for crossover point and dis-
continuous-mode equations. Discontinuous conduction
doesn’t affect normal Idle Mode operation.
ration ratings. In order to simplify the calculation, I
LOAD
may be used in place of I
if the inductor value has
PEAK
been set for LIR = 0.3 or less (high inductor values)
and 300kHz operation is selected. Low-inductance
resistors, such as surface-mount metal-film resistors,
are preferred.
Thre e ke y ind uc tor p a ra me te rs mus t b e s p e c ifie d :
inductance value (L), peak current (I
), and DC
PEAK
80mV
R
= ————
resistance (R ). The following equation includes a
SENSE
DC
I
PEAK
constant LIR, which is the ratio of inductor peak-to-peak
20 ______________________________________________________________________________________
MAXIM [ MAXIM INTEGRATED PRODUCTS ]
