LTC1625
U
W U U
APPLICATIONS INFORMATION
Thecorrespondingaveragecurrentdependsontheamount
of ripple current. Lower inductor values (higher ∆IL) will
reduce the load current at which Burst Mode operation
begins.
maximum values for RDS(ON), but not a minimum. A
reasonable, but perhaps overly conservative, assumption
is that the minimum RDS(ON) lies the same amount below
the typical value as the maximum RDS(ON) lies above it.
Consult the MOSFET manufacturer for further guidelines.
The output voltage ripple can increase during Burst Mode
operation if ∆IL is substantially less than IBURST. This will
primarily occur when the duty cycle is very close to unity
(VIN is close to VOUT) or if very large value inductors are
chosen. This is generally only a concern in applications
with VOUT ≥ 5V. At high duty cycles, a skipped cycle
causes the inductor current to quickly descend to zero.
However, it takes multiple cycles to ramp the current back
up to IBURST(PEAK). During this interval, the output capaci-
tor must supply the load current and enough charge may
be lost to cause significant droop in the output voltage. It
The LTC1625 includes current foldback to help further
limit load current when the output is shorted to ground. If
the output falls by more than half, then the maximum
sense voltage is progressively lowered from 150mV to
30mV. Under short-circuit conditions with very low duty
cycle, the LTC1625 will begin skipping cycles in order to
limit the short-circuit current. In this situation the bottom
MOSFET RDS(ON) will control the inductor current trough
rather than the top MOSFET controlling the inductor
current peak. The short-circuit ripple current is deter-
mined by the minimum on-time tON(MIN) of the LTC1625
(approximately 0.5µs), the input voltage, and inductor
value:
is a good idea to keep ∆IL comparable to IBURST(PEAK)
.
Otherwise, one might need to increase the output capaci-
tance in order to reduce the voltage ripple or else disable
Burst Mode operation by forcing continuous operation
with the FCB pin.
∆IL(SC) = tON(MIN) VIN/L.
The resulting short-circuit current is:
Fault Conditions: Current Limit and Output Shorts
30mV
1
2
I
=
+ ∆I
SC
L(SC)
The LTC1625 current comparator can accommodate a
maximum sense voltage of 150mV. This voltage and the
sense resistance determine the maximum allowed peak
inductor current. The corresponding output current limit
is:
R
ρ
T
DS(ON)(BOT)
Normally,thetopandbottomMOSFETswillbeofthesame
type. A bottom MOSFET with lower RDS(ON) than the top
may be chosen if the resulting increase in short-circuit
current is tolerable. However, the bottom MOSFET should
neverbechosentohaveahighernominalRDS(ON) thanthe
top MOSFET.
150mV
1
2
ILIMIT
=
– ∆IL
R
ρ
(
DS(ON))( )
T
The current limit value should be checked to ensure that
ILIMIT(MIN) > IO(MAX). The minimum value of current limit
generally occurs with the largest VIN at the highest ambi-
enttemperature,conditionswhichcausethehighestpower
dissipation in the top MOSFET. Note that it is important to
check for self-consistency between the assumed junction
temperature of the top MOSFET and the resulting value of
Inductor Core Selection
Once the value for L is known, the type of inductor must be
selected. High efficiency converters generally cannot
affordthecorelossfoundinlowcostpowderedironcores,
forcing the use of more expensive ferrite, molypermalloy
or Kool Mµ® cores. Actual core loss is independent of core
size for a fixed inductor value, but it is very dependent on
the inductance selected. As inductance increases, core
losses go down. Unfortunately, increased inductance
requires more turns of wire and therefore copper losses
will increase.
ILIMIT which heats the junction.
Caution should be used when setting the current limit
based upon RDS(ON) of the MOSFETs. The maximum
current limit is determined by the minimum MOSFET on-
resistance. Data sheets typically specify nominal and
Kool Mµ is a registered trademark of Magnetics, Inc.
11
Linear [ Linear ]
