KH560
DATA SHEET
With this total value derived, the required external C
x
is
developed by backing out the effect of the internal 10pF.
This, and an expression for the external C
x
without the
intermediate steps are shown below.
C
x
=
or
C
x
=
1
R
o
−
0.08
2
300
1
−
R
g
pF
10 C
t
10
−
C
t
without the compensating effect of load itself, would
otherwise require very large C
x
values.
Gain and Output Impedance Range
Figure 7 shows a plot of the recommended gain and
output impedances for the KH560. Operation outside of
this region is certainly possible with some degradation in
performance. Several factors contribute to set this range.
At very low output impedances, the required value of
feedback resistor becomes so low as to excessively load
the output causing a rapid degradation in distortion.
The maximum R
o
was set somewhat arbitrarily at 200Ω.
This allows the KH560 to drive into a 2:1 step down
transformer matching to a 50Ω load. (This offers
some advantages from a distortion standpoint.)
100
90
80
70
60
50
40
30
20
10
0
0
20
40
60
80 100 120 140 160 180 200
High Noise Region
Recommended
Region
Low R
f
or R
g
Region
20
18
16
14
12
10
8
6
4
2
0
5
10
15
20
25
30
35
40
45
50
55
R
o
= 100Ω
R
o
= 75Ω
R
o
= 50Ω
Maximally Flat Response
into a Matched Load
C
x
(pF)
No Load Gain
The plot in Figure 6 shows the required C
x
vs. gain for
several desired output impedances using the equations
shown above. Note that for lower R
o
’s, C
x
can get very
large. But, since the total compensation is actually the
series combination of C
x
and 10pF, going to very high
C
x
’s is increasingly ineffective as the total compensation
is only slightly changed. This, in part, sets the lower
limits on allowable R
o
.
Output Impedance (Ω)
Figure 7: Recommended Gain and
Output Impedance Range
For a given R
o
, the minimum gain shown in Figure 7 has
been set to keep the equivalent input noise voltage less
than 4nV/√Hz. Generally, the equivalent input noise volt-
age decreases with higher signal gains. The high gain
limit has been set by targeting a minimum R
g
of 10Ω or a
minimum R
f
of 100Ω.
Amplifier Configurations
The KH560 is intended for a fixed, non-inverting, gain
configuration as shown in Figure 1. The KH561 offers an
enhanced slew rate at the expense of higher long-term
thermal tail in the pulse response than the KH560. Due
to its low internal forward gain, the inverting node does
not present a low impedance, or virtual ground, node.
Hence, in an inverting configuration, the signals source
impedance will see a finite load whose value depends on
the output loading. Inverting mode operation can be best
achieved using a wideband, unity gain buffer with low
output impedance to isolate the source from this varying
load. A DC level can, however, be summed into the
inverting node to offset the output either for offset
correction or signal conditioning.
Accuracy Calculations
Several factors contribute to limit the achievable KH560
accuracy. These include the DC errors, noise effects,
9
No Load Voltage Gain
K
Figure 6: External Compensation Capacitance (C
x
)
A 0% small signal overshoot response can be achieved
by increasing C
x
slightly from the maximally flat value.
Note that this applies only for small signals due to slew
rate effects coming into play for large, fast edge rates.
Beyond the nominal compensation values developed
thus far, this external C
x
provides a very flexible means
for tailoring the frequency response under a wide variety
of gain and loading conditions. It is oftentimes useful to
use a small adjustable cap in development to determine
a C
x
suitable to the application, then fixing that value for
production. An excellent 5pF to 20pF trimmer cap for this
is a Sprague-Goodman part #GKX20000.
When the KH560 is used to drive a capacitive load, such
as an ADC or SAW device, the load will act to compen-
sate the response along with C
x
. Generally, considerably
lower C
x
values are required than the earlier develop-
ment would indicate. This is advantageous in that a low
R
o
would be desired to drive a capacitive load which,
REV. 1A January 2004
CADEKA [ CADEKA MICROCIRCUITS LLC. ]
